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UCT T PROD EMEN LETE REPLAC nter at BSO DED e O ort C om/tsc N MME ical Supp c RECODatanSheetntersil. h NO Tec w.i t our SIL or ww c conta INTER 1-888
EL4421, EL4422, EL4441, EL4442, EL4443, EL4444
January 1996, Rev. C FN7166
Multiplexed-Input Video Amplifiers
The EL44XX family of video multiplexed-amplifiers offers a very quick 8ns switching time and low glitch along with very low video distortion. The amplifiers have good gain accuracy even when driving low-impedance loads. To save power, the amplifiers do not require heavy loading to remain stable. The EL4421 and EL4422 are two-input multiplexed amplifiers. The -inputs of the input stages are wired together and the device can be used as a pin-compatible upgrade from the MAX453. The EL4441 and EL4442 have four inputs, also with common feedback. These may be used as upgrades of the MAX454. The EL4443 and EL4444 are also 4-input multiplexed amplifiers, but both positive and negative inputs are wired separately. A wide variety of gain- and phase-switching circuits can be built using independent feedback paths for each channel. The EL4421, EL4441, and EL4443 are internally compensated for unity-gain operation. The EL4422, EL4442, and EL4444 are compensated for gains of +2 or more, especially useful for driving back-matched cables. The amplifiers have an operational temperature of -40C to +85C and are packaged in plastic 8- and 14-pin DIP and 8and 14-pin SO. The EL44XX multiplexed-amplifier family is fabricated with Elantec's proprietary complementary bipolar process which gives excellent signal symmetry and is very rugged.
Features
* Unity or + 2-gain bandwidth of 80MHz * 70dB off-channel isolation at 4MHz * Directly drives high-impedance or 75 loads * 0.02% and 0.02 differential gain and phase errors * 8ns switching time * < 100mV switching glitch * 0.2% loaded gain error * Compatible with 3V to 15V supplies * 160mW maximum dissipation at 5V supplies
Ordering Information
PART NIMBER EL4421CN EL4421CS EL4422CN EL4422CS EL4441CN EL4441CS EL4442CN EL4442CS EL4443CN EL4443CS EL4444CN EL4444CS TEMP. RANGE -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C PACKAGE 8-Pin PDIP 8-Pin SO 8-Pin PDIP 8-Pin SO 14-Pin PDIP 14-Pin SO 14-Pin PDIP 14-Pin SO 14-Pin PDIP 14-Pin SO 14-Pin PDIP 14-Pin SO PKG. NO. MDP0031 MDP0027 MDP0031 MDP0027 MDP0031 MDP0027 MDP0031 MDP0027 MDP0031 MDP0027 MDP0031 MDP0027
Pinouts
EL4421/EL4422 (8-PIN PDIP, SO) TOP VIEW EL4441/EL4442 (14-PIN PDIP, SO) TOP VIEW EL4443/EL4444 (14-PIN PDIP, SO) TOP VIEW
Manufactured under U.S. Patent No. 5,352,987
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CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures. 1-888-INTERSIL or 321-724-7143 | Intersil (and design) is a registered trademark of Intersil Americas Inc. Copyright (c) Intersil Americas Inc. 2003. All Rights Reserved. Elantec is a registered trademark of Elantec Semiconductor, Inc. All other trademarks mentioned are the property of their respective owners.
EL4421, EL4422, EL4441, EL4442, EL4443, EL4444
Absolute Maximum Ratings (TA = 25C)
V+ VS VIN VIN Positive Supply Voltage . . . . . . . . . . . . . . . . . . . . . . 16.5V V+ to V- Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . .33V Voltage at any Input or Feedback . . . . . . . . . . . . V+ to VDifference between Pairs of Inputs or Feedback . . . . . .6V VLOGIC IIN IOUT PD Voltage at A0 or A1 . . . . . . . . . . . . . . . . . . . . . . -4V to 6V Current into any Input, Feedback, or Logic Pin . . . . . 4mA Output Current. . . . . . . . . . . . . . . . . . . . . . . . . . . . . 30mA Maximum Power Dissipation . . . . . . . . . . . . . See Curves
CAUTION: Stresses above those listed in "Absolute Maximum Ratings" may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA
Open-Loop DC Electrical Specifications
PARAMETER VOS Input Offset Voltage
Power supplies at 5V, TA = 25C, RL = 500, unless otherwise specified MIN -9 -7 -12 -24 -48 TYP 3 2 -5 -10 -20 60 '21 and '41 and '43 '22, '42 and '44 0.2 0.1 350 500 2.5 70 60 2.5 2.5 40 '21, '41, '43 '22, '42, '44 70 55 -16 0.8 EL4421 and EL4422 EL4441, EL4442, EL4443, and EL4444 13 11 16 500 750 3 90 70 3 3.5 80 80 64 -8 0 2.0 14 MAX 9 7 0 0 0 350 0.6 0.6 A A A nA % V/V V/V V/V V dB dB V V mA dB dB A V mA UNITS mV
DESCRIPTION '21, '41, and '43 '22, '42, and '44
IB IFB
Input Bias Current, Positive Inputs Only of the '21, '22, '41, '42, and All Inputs of the '43 and '44 Input Bias Currents of Common Feedback Input Offset Currents of the '43 and '44 Gain Error (Note 1) '21 and '22 '41 and '42
IOS EG
AVOL
Open-Loop Gain (Note 1)
EL4443 EL4444
VIN CMRR PSRR CMIR VOUT ISC FT
Input Signal Range, EL4421 and EL4441 (Note 2) Common-Mode Rejection Ratio, EL4443 and EL4444 Power Supply Rejection Ratio VS from 5V to 15V Common-Mode Input Range EL4443 and EL4444 (Note 3) Output Swing Output Short-Circuit Current Unselected Channel Feedthrough Attenuation (Note 1)
ILOGIC VLOGIC IS
Input Current at A0 and A1 with Input = 0V and 5V Logic Valid High and Low Input Levels Supply Current
NOTES: 1. The '21, '41, and '43 devices are connected for unity-gain operation with 75 load and an input span of 1V. The '22, '42, and '44 devices are connected for a gain of +2 with a 150 load and a 1V input span with RF = RG = 270. 2. The '21 and '41 devices are connected for unity gain with a 3V input span while the output swing is measured. 3. CMIR is assured by passing the CMRR test at input voltage extremes.
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EL4421, EL4422, EL4441, EL4442, EL4443, EL4444
Closed-Loop AC Electrical Specifications
Power supplies at 5V. TA = 25C, for EL4421, EL4441, and EL4443 AV = +1 and RL = 500, for EL4422, EL4442, and EL4444 AV = +2 and RL = 150 with RF = RG = 270 and CF = 3pF; for all CL = 15pF MIN TYP 80 65 10 0.5 EL4421, EL4441, EL4443 EL4422, EL4442, EL4444 EL4421, EL4441, EL4443 EL4422, EL4442, EL4444 EL4421, '41, '43 (VS = 12V) EL4421, '41, '43 (VS = 5V) EL4422, '42, '44 (VS = 12V) EL4422, '42, '44 (VS = 5V) dO Differential Phase Error, VOFFSET EL4421, '41, '43 (VS = 12V) between -0.7V and +0.7V EL4421, '41, '43 (VS = 5V) EL4422, '42, '44 (VS = 12V) EL4422, '42, '44 (VS = 5V) TMUX Multiplex Delay Time, Logic Threshold to 50% Signal Change Peak Multiplex Glitch EL4421, '22 EL4441, '42, '43, '44 EL4421, '22 EL4441, '42, '43, '44 ISO Channel Off Isolation at 3.58MHz (See Text) EL4421, EL4441, EL4443 EL4422, EL4442, EL4444 150 180 200 240 18 14 0.01 0.10 0.02 0.11 0.01 0.1 0.02 0.15 8 12 70 100 76 63 MAX UNITS MHz MHz MHz dB V/sec V/sec nV/Hz nV/Hz % % % % nsec nsec mV mV dB dB
PARAMETER BW - 3dB
DESCRIPTION -3dB Small-Signal Bandwidth EL4421, '41, '43 EL4422, '42, '44
BW 0.1dB Peaking SR
0.1dB Flatness Bandwidth Frequency Response Peaking Slewrate, VOUT between -2.5V and +2.5V, VS = 12V Input-Referred Noise Voltage Density Differential Gain Error, VOFFSET between -0.7V and +0.7V
VN
dG
VGLITCH
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EL4421, EL4422, EL4441, EL4442, EL4443, EL4444 Typical Performance Curves
EL4421, EL4441, and EL4443 Small-Signal Transient Response VS = 5V, RL = 500 EL4421, EL4441, and EL4443 Large-Signal Response VS = 12V, RL = 500
EL4421, EL4441, and EL4443 Frequency Response for Various Gains
EL4422, EL4442, and EL4444 Frequency Response for Various Gains
EL4421, EL4441, and EL4443 Frequency Response for Various Loads VS = 5V, AV = +1
EL4422, EL4442, and EL4444 Frequency Response for Various Loads VS = 5V, AV = +2
Frequency Response for Various Loads VS = 15V, AV = + 1
EL4422, EL4442, and EL4444 Frequency Response for Various Loads VS = 15V, AV = +2
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EL4421, EL4422, EL4441, EL4442, EL4443, EL4444 Typical Performance Curves
(Continued)
EL4444 Open-Loop Gain and Phase vs. Frequency
EL4443 Open-Loop Gain and Phase vs. Frequency
EL4421, EL4441, and EL4443 -3dB Bandwidth, Slewrate, and Peaking vs. Supply Voltage
EL4422, EL4442, and EL4444 -3dB Bandwidth, Slewrate, and Peaking vs. Supply Voltage
EL4421, EL4441, and EL4443 Bandwidth, Slewrate, and Peaking vs. Temperature, AV = +1, RL =500
EL4422, EL4442, and EL4444 Bandwidth, Slewrate, and Peaking vs. Temperature, AV = +2, RL = 150, RI = RG = 270, CF = 3pF
EL4421, EL4441, and EL4443 -3dB Bandwidth and Gain Error vs. Load Resistance
Input Noise vs. Frequency
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EL4421, EL4422, EL4441, EL4442, EL4443, EL4444 Typical Performance Curves
(Continued)
EL4422, EL4442, and EL4444 Differential Gain and Phase Error vs. Input Offset; AV = +2, RL = 150, F = 3.58MHz
EL4421, EL4441, and EL4443 Differential Gain and Phase Errors, vs. Input Offset, AV = +1, RL = 500, F = 3.58MHz
EL4421, EL4441, and EL4443 Differential Gain and Phase Error vs. Load Resistance; AV = +1, F = 3.58MHz, VOFFSET = 0 0.714V
EL4443 and EL4444 Open-Loop Gain vs. Load Resistance
Change in VOS, AV, and IB with Supply Voltage
Change in VOS, IB, and AV vs. Temperature
Switching Waveforms Switching from Grounded Input to Uncorrelated Sinewave and Back
Channel-to-Channel Switching Glitch
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EL4421, EL4422, EL4441, EL4442, EL4443, EL4444 Typical Performance Curves
(Continued)
EL4422, EL4442, and EL4444 Unselected Channel Feedthrough vs. Frequency
EL4421, EL4441, and EL4443 Unselected Channel Feedthrough vs. Frequency
EL4443 and EL4444 Input and Output Range vs. Supply Voltage (Output Unloaded)
Supply Current vs. Supply Voltage
Supply Current vs. Temperature
8-Pin Package Power Dissipation vs. Ambient Temperature
14-Pin Package Power Dissipation vs. Ambient Temperature
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EL4421, EL4422, EL4441, EL4442, EL4443, EL4444 Applications Information
General Description
The EL44XX family of video mux-amps are composed of two or four input stages whose inputs are selected and control an output stage. One of the inputs is active at a time and the circuit behaves as a traditional voltage-feedback op-amp for that input, rejecting signals present at the unselected inputs. Selection is controlled by one or two logic inputs. The EL4421, EL4422, EL4441, and EL4442 have all -inputs wired in parallel, allowing a single feedback network to set the gain of all inputs. These devices are wired for positive gains. The EL4443 and EL4444, on the other hand, have all +inputs and -inputs brought out separately so that the input stage can be wired for independent gains and gain polarities with separate feedback networks. The EL4421, EL4441, and EL4443 are compensated for unity-gain stability, while the EL4422, EL4442, and EL4444 are compensated for a fed-back gain of +2, ideal for driving back-terminated cables or maintaining bandwidth at higher fed-back gains. For example, within these constraints, we can power the EL44XX's from +5V and +12V without a negative supply by using these connections.
FIGURE 2. USING THE EL44XX MUX AMPS WITH +5V AND +12V SUPPLIES
Switching Characteristics
The logic inputs work with standard TTL levels of 0.8V or less for a logic 0 and 2.0V or more for a logic 1, making them compatible for TTL and CMOS drivers. The ground pin is the logic threshold biasing reference. The simplified input circuitry is shown in Figure 1 below.
The logic input(s) and ground pin are shifted 2.5V above system ground to correctly bias the mux-amp. Of course, all the signal inputs and output will have to be shifted 2.5V above system ground to ensure proper signal path biasing. A final caution: the ground pin is also connected to the IC's substrate and frequency compensation components. The ground pin must be returned to system ground by a short wire or nearby bypass capacitor. In Figure 2, the 22k resistors also serve to isolate the bypassed ground pin from the +5V supply noise.
Signal Amplitudes
Signal input and output voltages must be between (V-)+2.5V and (V+)-2.5V to ensure linearity. Additionally, the differential voltage on any input stage must be limited to 6V to prevent damage. In unity-gain connections, any input could have 3V applied and the output would be at 3V, putting us at our 6V differential limit. Higher-gain circuit applications divide the output voltage and allow for larger outputs. For instance, at a gain of +2 the maximum input is again 3V and the output swing is 6V. The EL4443 or EL4444 can be wired for inverting gain with even more amplitude possible. The output and positive inputs respond to overloading amplitudes correctly; that is, they simply clamp and remain monotonic with increasing +input overdrive. A condition exists, however, where the -input of an active stage is overdriven by large outputs. This occurs mainly in unity-gain connections, and only happens for negative inputs. The overloaded input cannot control the feedback loop correctly and the output can become non-monotonic. A typical scenario has the circuit running on 5V supplies, connected for unity gain, and the input is the maximum 3V. Negative input extremes can cause the output to jump from -3V to
FIGURE 1. SIMPLIFIED LOGIC INPUT CIRCUITRY
The ground pin draws a maximum DC current of 6A, and may be biased anywhere between (V-) +2.5V and (V+) -3.5V. The logic inputs may range from (V-)+2.5V to V+, and are additionally required to be no more negative than V(Gnd pin)-4V and no more positive than V(Gnd pin)+6V.
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EL4421, EL4422, EL4441, EL4442, EL4443, EL4444
around -2.3V. This will never happen if the input is restricted to 2.5V, which is the guaranteed maximum input compliance with 5V supplies, and is not a problem with greater supply voltages. Connecting the feedback network with a divider will prevent the overloaded output voltage from being large enough to overload the -input and monotonic behavior is assured. In any event, keeping signals within guaranteed compliance limits will assure freedom from overload problems. The input and output ranges are substantially constant with temperature. Where TD, max is the maximum die temperature, 150C for reliability, less to retain optimum electrical performance TA, max is the ambient temperature, 70 for commercial and 85C for industrial range RTH is the thermal resistance of the mounted package, obtained from data sheet dissipation curves The most difficult case is the SO-8 package. With a maximum die temperature of 150C and a maximum ambient temperature of 85, the 65 temperature rise and package thermal resistance of 170/W gives a maximum dissipation of 382mW. This allows a maximum supply voltage of 9.2V for the EL4422 operated in our example. If the EL4421 were driving a light load (RPAR), it could operate on 15V supplies at a 70 maximum ambient. The EL4441 through EL4444 can operate on 12V supplies in the SO package, and all parts can be powered by 15V supplies in DIP packages.
Power Supplies
The mux-amps work well on any supplies from 3V to 15V. The supplies may be of different voltages as long as the requirements of the Gnd pin are observed (see the Switching Characteristics section for a discussion). The supplies should be bypassed close to the device with short leads. 4.7F tantalum capacitors are very good, and no smaller bypasses need be placed in parallel. Capacitors as small as 0.01F can be used if small load currents flow. Single-polarity supplies, such as +12V with +5V can be used as described in the Switching Characteristics section. The inputs and outputs will have to have their levels shifted above ground to accommodate the lack of negative supply. The dissipation of the mux-amps increases with power supply voltage, and this must be compatible with the package chosen. This is a close estimate for the dissipation of a circuit: PD = 2VS x Is,max + (VS-VO) x VO/RPAR Where IS, max is the maximum supply current VS is the supply voltage (assumed equal) VO is the output voltage RPAR is the parallel of all resistors loading the output For instance, the EL4422 draws a maximum of 14mA and we might require a 2V peak output into 150 and a 270 +270 feedback divider. The RPAR is 117. The dissipation with 5V supplies is 191mW. The maximum Supply voltage that the device can run on for a given PD and the other parameter is VS, max = (PD + VO2/RPAR)/2IS + VO/RPAR) The maximum dissipation a package support is PD, max = (TD, max-TA, max)/RTH
Output Loading
The output stage of the mux-amp is very powerful, and can source 80mA and sink 120mA. Of course, this is too much current to sustain and the part will eventually be destroyed by excessive dissipation or by metal traces on the die opening. The metal traces are completely reliable while delivering the 30mA continuous output given in the Absolute Maximum Ratings table in this data sheet, or higher purely transient currents. Gain or gain accuracy degrades only 10% from no load to 100 load. Heavy resistive loading will degrade frequency response and video distortion only a bit, becoming noticeably worse for loads < 100. Capacitive loads will cause peaking in the frequency response. If capacitive loads must be driven, a small-valued series resistor can be used to isolate it. 12 to 51 should suffice. A 22 series resistor will limit peaking to 2.5dB with even a 220pF load.
Input Connections
The input transistors can be driven from resistive and capacitive sources but are capable of oscillation when presented with an inductive input. It takes about 80nH of series inductance to make the inputs actually oscillate, equivalent to four inches of unshielded wiring or about 6 of unterminated input transmission line. The oscillation has a characteristic frequency of 500MHz. Often simply placing one's finger (via a metal probe) or an oscilloscope probe on the input will kill the oscillation. Normal high-frequency construction obviates any such problems, where the input source is reasonably close to the mux-amp input. If this is not possible, one can insert series resistors of around 51 to de-Q the inputs.
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EL4421, EL4422, EL4441, EL4442, EL4443, EL4444
Feedback Connections
A feedback divider is used to increase circuit gain, and some precautions should be observed. The first is that parasitic capacitance at the -input will add phase lag to the feedback path and increase frequency response peaking or even cause oscillation. One solution is to choose feedback resistors whose parallel value is low. The pole frequency of the feedback network should be maintained above at least 200MHz. For a 3pF parasitic, this requires that the feedback divider have less than 265 impedance, equivalent to two 510 resistors when a gain of +2 is desired. Alternatively, a small capacitor across RF can be used to create more of a frequency-compensated divider. The value of the capacitor should match the parasitic capacitance at the -input. It is also practical to place small capacitors across both the feedback resistors (whose values maintain the desired gain) to swamp out parasitics. For instance, two 10pF capacitors across equal divider resistors will dominate parasitic effects and allow a higher divider resistance. The other major concern about the divider concerns unselected-channel crosstalk. The differential input impedance of each input stage is around 200k. The unselected input's signal sources thus drive current through that input impedance into the feedback divider, inducing an unwanted output. The gain from unselected input to output, the crosstalk attenuation, if RF/RIN. In unity-gain connection the feedback resistor is 0 and very little crosstalk is induced. For a gain of +2, the crosstalk is about -60dB.
FEEDTHROUGH OF EL4421 AT 3.58MHz CHANNEL SELECT INPUT, A0 0 1 IN1 Selected -93dB IN2 -88dB Selected
Switching Glitches
The output of the mux-amps produces a small "glitch' voltage in response to a logic input change. A peak amplitude of only about 90mV occurs, and the transient settles out in 20ns. The glitch does not change amplitude with different gain settings. With the four-input multiplexers, when two logic inputs are simultaneously changed, the glitch amplitude doubles. The increase can be a avoided by keeping transitions at least 6ns apart. This can be accomplished by inserting one gate delay in one of the two logic inputs when they are truly synchronous.
Feedthrough Attenuation
The channels have different crosstalk levels with different inputs. Here is the typical attenuation for all combinations of inputs for the mux-amps at 3.58MHz:
FEEDTHROUGH OF EL4441 AND EL4443 AT 3.58MHz SELECT INPUTS, A1 A0 00 01 10 11 IN1 Selected -80dB -101dB -96dB IN2 -77dB Selected -76dB -84dB IN3 -90dB -77dB Selected -66dB IN4 -92dB -90dB -66dB Selected
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